This series of articles deal with the more technical aspects of antennas and the practical theory behind their use. You will find this guide to be a pragmatic approach to antenna theory. The views expressed here are the author’s and are not meant to be the definitive text on the subject. You should also be armed with the knowledge that there may be changes from time to time where technology advances and the author deems it approprate to update the text.

You should do your won research and fill in where there are
“learning gaps”.

Much of the material in this series is derived from publications by
the ARRL. Namely,

The ARRL Handbook ®

and

The ARRL Antenna Book ®.

You should consider those publications reference material in this cursory study of a very complex subject. The most recent editions are available from the ARRL Store online and can be seen at many hamfests, but may vary in quality from used to mint conditon, over many past versions. Any should be considered a valuable addition to your reference library on antennas.

I hope you enjoy this. Please email me if you have questions or would
like to see a particular subject enhanced.

For this discussion we will review the information supplied previously in our description of the complex nature of antennae. The illustration below is a discreet visualization of a coax or feedline such as twinlead or open wire “ladder line”. It is not difficult to see the interactive effects of the two conductors that make up the feedline. As with our vertical antenna, feedlines exhibit inductive properties along the length, and shunt capacitance between the conductors.

The characteristic impedance of feedlines is expressed in ohms for
simplicity. While there is some discussion as to how short a line must
be to exhibit its characteristic impedance, there is no controversy
when using 100 feet as a nominal length to publish impedances, velocity
factor, and I^{2}R loss. These figures are important to the ham
when evaluating efficiency of an operational antenna on various bands.

To illustrate this, let’s create a scenario that may be common for many amateur operators.

The characteristic impedance of feedlines is often expressed in ohms for simplicity. While there is some discussion as to how short a line must be to exhibit its characteristic impedance, there is no controversy when using 100 feet as a nominal length to publish impedances, velocity factor, and I2R loss. These figures are important to the ham when evaluating efficiency of an operational antenna on various bands. To illustrate this, let's create a scenario that may be common for the typical ham shack.

Our hypothetical antenna is a 100 foot long flat–top dipole with 100 feet of RG–8U coax. We will use calculated measurements of antenna impedances and the resulting feedline loss due to SWR at various frequencies. This system is completely unoptimized to illustrate the losses involved in un–matched systems.

At our 80 meter frequency, this antenna exhibits a very low impedance of only 18 ohms. Even with a balun, this antenna will have a very high SWR and will require a matching network or antenna tuner to operate on 80 meters. At the other end of the HF frequency spectrum is our 100 foot dipole at 28.400 Mhz. The following chart indicates the impedances at that band of frequencies.

Once again the antenna characteristic impedances are well above a good operational limit. This is not to say that the antenna is not resonate. You will notice from the chart that it is indeed resonate at 28.205 MHz. However, the real impedance is some 500-700 ohms. Once again this antenna on 10 meters will require a matching network or tuner to operate with our equipment and 50 ohm coax.

From our discussions so far, it should be easy for you to conclude that the SWR on these band limits would be very high. Aside from the destructive implications of high voltage arching and matching network saturation, etc. we should consider how much of our signal will actually be radiated. This is a consideration when taking in to account the losses of our feed line at this very high SWR condition. This is especially true when using a matchbox in the shack instead of a matching network at the feedpoint of the antenna or a tuner at the antenna. You need only recall our admonition about what the tuner does.

The tuner does not eliminate the impedance mismatch between the antenna and the coax when located in the shack. So, if the antenna to coax mismatch is still there, power will be lost in the feedline. How much is lost depends on the SWR and the rated loss per 100 feet given by the manufacturer. Our scenario uses RG–8U cable that has a solid PE dielectric. This cable is rated at 50 ohms and a loss of .211 db per 100 ft. for 3 mHz. That same coax will have .68 db loss per 100 ft. at 30 mHz. This rating assumes a good impedance match. The following chart indicates how much additional loss could be expected under SWR conditions we may find in our shack.

With only a 3:1 SWR at 30 mHz, the RG–8U cable will have an additional .373 db. The rated .68 plus loss due to high SWR amounts to 1.052 db loss at 30 mHz. This loss doubles to 1.969 db at 7:1 SWR and etc.

It is not difficult to see that the I^{2}R losses are not
significant in the HF range for RG–8U cable. However, losses
above 30 mHz are. RG–8U coax, while very efficient on HF
frequencies, is only appropriate above 30 mHz where there is a very
good match between the coax and the antenna. The well made RG–8U
cable we speak of has a loss of 1.547 db at 145 mHz when perfectly
matched. This doesn’t sound like much, but translated to power
delivered to the antenna of only 70.129 watts, it means a 30% loss of
power in the coax. Our chart for additional loss due to SWR is still appropriate. So a 3:1 SWR should be rendered as 2.228 db loss at 145
Mhz. A SWR of 6:1 could yield as much as 3.396 db loss per 100 feet of cable (only 45.85 watts reaches the antenna for 100 watts in). Quite a difference, to say the least. The more appropriate choice of cable is ¾ inch hardline (either PE foam or air helix) with only .8 db loss per 100 ft. (2.03 db in our 6:1 SWR case in point – 62.989 watts delivered to the antenna).

Compare the figures for RG–8U to the more common RG–58A. Losses for this type cable are 2.095 db per 100 ft. at 30 mHz – twice the db (that translates to 4.26 times as much power loss) as RG–8U! Knowing what we know about signal attenuation and loss, RG–58A, AU, AX become inappropriate for frequencies above 30 mHz where the cable exceeds more than 20 feet. In fact, if we take a detailed look at the cable specs, power limits for this type of cable are in the under 500 watt safety range even in the HF frequencies.

Here is a good site to visit for data on different types of coax and twin wire feed:

http://www.ocarc.ca/coax.htm

Now lets look at a non–coaxial feedline. The common twin wire feed line in use today is fondly called “ladderline” or “window” twin line. This descriptive name is due to the way the dielectric is manufactured with rectangular holes cut in the space between the wires at regular intervals. The dielectric is normally brown or black polyethylene. The holes are used to lower the velocity factor (i.e. propagation delay) from where it would be with solid dielectric the entire length as with TV twin lead. As a general rule, the lower the velocity factor (i.e. the larger the number approaching 1.00), the lower the attenuation losses of the feedline. Twin–wire “window” line and open wire “ladder” line provide the best velocity factor (i.e. The larger numbers approaching 1.00) and also the lowest loss of all types of coax and feed line types with the possible exception of 6 inch air dielectric nitrogen filled coaxial hardline (usually for commercial broadcast use).

Every curious ham radio enthusiast and CB’er has heard that it is best to “cut your coax to length” to work “right”. What does that mean – “cut it to length”? This phrase references the same phenomenon we have been studying about complex impedances on antennas and feedlines. It is a fact that coax or twin wire “ladderline” can be resonant too.

However, a number of factors are in play when calculating the correct wavelength of feedline. The primary determining factor is called the velocity factor. Earlier we described velocity factor to mean the delay in propagation of RF along the feedline with a solid dielectric versus transmission wires separated by air. The reference of air dielectric is a 1.00 velocity factor (no delay). Solid PE dielectric very often provides a .66 to .68 velocity factor. Foam PE velocity factor will vary according to the foam density from .72 to .87. Since foam PE does not hold its shape very well, a loss of form factor will cause additional losses of other types as well as impedance variations in a wide range. The wavelength of coax is measured by calculating the wavelength and multiplying the result by the velocity factor. For instance, the half–wavelength of 20 meters is 10 meters or about 32.7 feet. The physical half-wavelength of RG–8U cable will be much shorter (approximately 21.6 to 22.79 feet depending on the quality of the cable used). For comparison, the 6 inch nitrogen filled hardline coax mentioned previously has a velosity factor of .95 with only .077 db loss at frequencies up to 1.2 gHz. The very low velocity factor makes figuring the physical length of “tuned” coax easy. The ARRL Antenna Book provides a CD ROM that has a calculator program to do this figuring for you. You may also visit the Web site included above.

So why would you want to cut your coax to length? In practice, there are several occasions that precise lengths of coax are not only appropriate, but desirable. One situation was mentioned in an earlier chapter when talking about matching antenna impedances to coax. The following illustration is an example.

This strange looking arrangement provides an impedance transformation of 4:1 just as a transformer type balun would. The advantage is that this balun is much easier and cheaper to construct. The “U” shaped part is made from higher impedance cable like RG–214 or other low loss 75 to 150 ohm coax. The length is fixed at ½ the wavelength of the center frequency to be matched. This type of matching arrangement is most often seen at VHF and UHF frequencies (less frequently on 6 meters) due to the length of coax needed for matching. The length needed for matching 10 meters (e.g. 28.350 Mhz ) would be 11.45 feet assuming a velocity factor of .66. You could see the impracticality of using this kind of balun on 40 or 80 meters.

Another situation would be where we wish to tune out the reactive part of an otherwise effective antenna. Let’s assume our antenna radiates well as a 5/8 wave length vertical. This is not a resonate antenna at 50 ohms. At resonance, it calculates to be 12 -j125. Coax exhibits an unusual phenomenon when cut to very short lengths (less than 1/4th wavelength). If measured with both ends open, the coax will exhibit very capacitive characteristics. While shorting one end will cause just the opposite reaction. This phenomenon becomes happily convenient when we wish to offset minor reactive and impedance variations in a non–resonate antenna. Our 5/8 wave vertical can be matched with a shorted stub of coax that will equal and oppose the highly capacitive value of the antenna alone. The combined result is a real impedance very near our 50 ohm coax. The diagram below shows how the antenna wire and coax are combined to form the stub matched antenna–coax connection.

If this combination is not a high enough impedance, a fractional length of 75 ohm coax can be added in series with the antenna before the stub to raise the overall impedance. Millions of CB and marine antenna have been manufactured to just such a specification.

The third situation is appropriate only when an antenna is used on one band or one band primarily with little use on other frequencies. The single–band, single–use antenna system will likely contain a feedline that is a ½ wavelength multiple of the center operating frequency. In this way, the coax contributes little to the system other than transmission of RF from rig to antenna. The match is very close and power delivered to the antenna is as efficient as possible.

This last situation is of particular importance due to a phenomenon
that occurs on sections of coax or feedline that are ½
wavelength. When the line length is a multiple of ½ wavelength,
the input resistance is equal to the load resistance. In simpler terms,
the impedances seen at the rig end of the coax very nearly equal the
impedances at the antenna feedpoint terminals. It does not matter
whether the impedance exists at the antenna end or the rig end. It does
not matter whether the impedance is a simple resistive value or complex
with multiple conjugate values (as expressed by our R+jX notation).
Sections of coax or “ladderline” in ½ wavelength can
be added or subtracted without changing the other system performance
conditions, with the possible exception of I^{2}R losses. This
means that half wavelength sections will exhibit their characteristic
impedances when one end is shorted. When the need arises to combine two
impedances to result in a closer match to our coax, we use this type of
arrangement. Practically known as the ½ wave stub, matching of
this type has been used on a variety of antenna types for most of the
existence of ham radio. A very good illustration of stub tuning is
given in the ARRL Antenna Book Chapter 18 page 27 (20th Edition). The 6
meter Yagi shown in the illustration at the bottom of the page is
resonated with a ½ wavelength “hairpin” stub and a
coaxial stub is used as a balun. Both methods have been discussed here
in previous text.

The exact opposite is true of ¼ wavelength lines. The impedance seen at the rig is an inverse function of the antenna end. If the antenna end is very low impedance, the rig end of the ¼ wave line will be a very high impedance. In sections shorter than ¼ wavelength, the coax will exhibit wave mechanics as explained earlier (shorted as as inductive reactance and open acts as capacitive reactance).

One note of caution is appropriate in this discussion. When highly reactive loads are used with commonly used transmission lines, especially coax, the overall losses resulting can be of unacceptable levels.

The reasons for this type of wave reflection mechanics are numerous and mathematically complex. For the purpose of this document it is sufficient to state this phenomenon in simple terms. Detailed explanatory text is available in the referenced text.

73 AD5XJ

Rev. 1.00 2018-01-08 AD5XJ