This series of articles deal with the more technical aspects of antennas and the practical theory behind their use. You will find this guide to be a pragmatic approach to antenna theory. The views expressed here are the author’s and are not meant to be the definitive text on the subject. You should also be armed with the knowledge that there may be changes from time to time where technology advances and the author deems it approprate to update the text.
You should do your won research and fill in where there are
Much of the material in this series is derived from publications by the ARRL. Namely,
The ARRL Handbook ®
The ARRL Antenna Book ®.
You should consider those publications reference material in this cursory study of a very complex subject. The most recent editions are available from the ARRL Store online and can be seen at many hamfests, but may vary in quality from used to mint conditon, over many past versions. Any should be considered a valuable addition to your reference library on antennas.
I hope you enjoy this. Please email me if you have questions or would
like to see a particular subject enhanced.
Our discussion this time is not specifically about SWR. It is about the more conventional horizontal dipole and the simplified theory behind dipole based designs. For clarity, we will prefer a reference to the so–called “flat top” dipole. This is for illustrative purposes only, as other types of dipoles are just as effective but have more variable characteristics. We will keep our discussion relatively simple for now.
Dipoles are what is known as a linear current device; meaning current in the conductors of a dipole flow in one direction (the straight line of the conductor). All currents in the dipole flow in the same direction at the same time. The illustration below shows graphically what this means.
When the half–wave dipole is suspended in space, it will exhibit
some known and predictable characteristics. The most important of these
is impedance. The approximate (approximate because different
calculations yield different results) known impedance of the
half–wave dipole in space is expressed as:
Recent empirical measurements by astronauts have confirmed much of the mathematical research offered so far. Even so, deep space is the only environment to prove the formulas definitively.
Several things should be gleaned from this value:
You will recall from our discussion that a dipole in free space does not have to suffer the effects of ground. This predictability is why scientists use the free space model as a statistical reference. Let's see what the ground does to our isotropic dipole as we mount it one wavelength above average ground.
It should be obvious, with some observation of the graph, that the
overall impedance has lowered substantially. Instead of 74.2, the
impedance is now about 72.5. As well, the resonant frequency has
changed, or put another way; the resonant length for our original
frequency is now much longer. This effect of ground proximity is true
for any height, bearing in mind any change in height will make
substantial changes in impedance. The following graph shows the effect
of ground on the impedance at the feedpoint.
Now lets mount it at a more reasonable height of say 20 ft (6.1142 meters). This height is approximate to 0.28664 wavelengths at our hypothetical frequency. A little more than quarter wavelength at our test frequency. The impedance at this height is: 96.884+j1816. WOW! What a difference the ground makes! Now we have a problem. Not only is the impedance much higher than our coax impedance, it is much too long to be resonant for our test frequency. Take a look at the impedance plot for it:
If nothing else is changed, the SWR on this antenna will be well over 2:1 for 50 ohm coax. To rectify this situation we need to make a slight shift in our analysis. Recall in a previous discussion we said that the balun device acts as a isolation and balancing transformer. Well, it also can transform impedances as well. To do this we construct a balun that has a 2:1 impedance ratio. The input side will be 50 ohms and the antenna side will be 100 ohms. Problem solved! Almost.
We now need a way to calculate the resonant point for 100 ohms instead of 50 ohms, because the balun transforms the impedances to match our transmission line, we see the antenna transformed to 50 ohms at the coax. Tuning our antenna should now be possible through normal means of lengthening or shortening the physical elements.
If we analyze the impedance plot for this near–earth dipole we can make an informed guess that we have to shorten the elements in order to bring it to resonance. We must shorten the length by about 2% vs. our 1 wavelength height. This resonant point yields an impedance of 93.4+j0.051. Because this antenna height will not allow us to use conventional impedance matching, we will not see extremely low SWR readings without using the impedance matching balun mentioned before.
This does not mean that the antenna is not effective. It simply means that we must understand the operating limitations of our station and antenna system.
Close-to-earth antennas such as we have described are not uncommon and should not be avoided when faced with no other alternative. The unique characteristics and limitations of this type of antenna should be anticipated, however.
But, what if we were not able to erect a completely horizontal dipole? This too is a common situation faced by hams everywhere. The resulting configuration might be one of the alternative dipole types – the inverted “V”, the “slopper”, the folded dipole, the “bent” dipole or “half square”, or the less common horizontal “V”. All of these alternatives present unique characteristics that are widely differing and can be challenging to make efficient in your unique antenna location. Do not hesitate to enlist the help of an experienced “Elmer” in modeling and analyzing difficult situations for these alternative antenna types or unique installations of conventional dipoles.
Beyond SWR, we must look at the other aspects to consider when analyzing antenna installations. One of the more important would be the radiation pattern. While actual radiation patterns will vary greatly with each installation, particular antenna types exhibit predictability in radiation patterns where unobstructed by environment. In the case of the horizontal dipole, we can examine the classic example of the half wavelength model at a common height. Our example previously was at 20 feet. The signal strength plots shown below indicate a common radiation pattern of close–to–earth antennae.
The antenna axis is along the Y coordinates of the polar graph and the elevation plot is shown viewed from the end of the wire. Because of the “bubble” like appearance of the elevation pattern, this type of antenna is often referred to as a “cloud warmer”. Depending on atmospheric conditions, this particular pattern can be invaluable.
Now lets compare this to the same antenna placed at 33 feet (10.09
No longer are we “warming the clouds”. The radiation
pattern has flattened considerably. Now there is a prominent radiation
lobe at 29.5 deg. Elevation and gain has increased by almost 3 db. Just
as importantly, the impedances are more manageable at 77 ohms. We can
get a much better match to 75 ohm coax with this antenna or 50 ohm coax
with a 1.5:1 balun. Of course, just as we observed before, we had to
adjust the length of the wire to make it resonate at this height versus
the length at 20 feet.
We made reference to alternative versions of the “flat top” dipole earlier. We only have space to demonstrate one of the many we mentioned – the inverted “V”. The illustration shown below is for an inverted “V” dipole at our test frequency with the feedpoint raised to 33 ft. and the ends drooping to within 8 feet of the ground. Admittedly, this is not ideal (the ideal angle for the inverted “V” is much more than 45 deg.) but it is much more common.
It can be seen from the model that the radiation pattern is common for a close–to–earth antenna but the impedance is brought to very low values by the close proximity of the element ends to ground (this directly translates to high SWR on 50 ohm coax). This may be outside the range of most tuners and common mode radiation (i.e. coax radiation) may be unacceptable when using an in–shack tuner. When practicable, raising the ends to the ideal height would produce a much more desirable situation as evidenced by the plot below.
The characteristics of this situation make it much more manageable by station equipment with much less undesirable effects (common mode radiation). You should also notice the reduction of the “cloud warming” radiation. The very high angle of take–off (45 deg.) makes this a very good short to medium range antenna at this frequency.
Is it possible to have a near–to–earth antenna that matches our coax better and provides adequate performance? As someone was once heard to say “Anything is possible – some things just take a little longer”. Seriously, it is possible with the inverted “V” to get a good match, even on 40 meters and below, at a common height. The following chart shows what would possibly result if you placed a properly tuned 40 meter inverted “V” at 40 feet with the ends at only 8 feet above ground. We have tuned the length to be resonant on the center of the 40 meter band. Also included is the SWR plot for a 300 kHz sweep of that band.
Potential users of this type of antenna should remember that it exhibits the displayed characteristics at 40 meter frequencies and the stated height only. A completely different set of characteristics will be observed on other bands, at other frequencies, etc. and may not be as desired or expected.
By now it should be obvious that objects close to the radiating elements cause considerable changes in the impedances and radiation patterns of the various versions of dipoles.
Up to this point we have discussed dipoles that are resonate. But, dipoles can be effective radiators when of non-resonate lengths as well, provided you find an efficient way to feed it. The classic non–resonate dipole antenna is the open wire feed dipole. This antenna can be of any length, but traditionally a length of 100-120 feet is not uncommon. The next illustration is of a classic non–resonate dipole antenna feedpoint impedances in several bands.
This 100 foot dipole is up 12 meters (approx. 39 feet) and feed with open wire line that is 600 ohms characteristic impedance. One of the first things to notice is that the antenna resonate point is out of the ham bands. Since the reactive values never cross the zero line, we can conclude that it is not resonate at any amateur frequency. We can also see that the SWR is quite high at all frequencies in band.
Despite the noted characteristics, this is a very effective antenna and great all around performer. How can this be? you ask. It is possible because we have feed the antenna with a very efficient feed line that can accommodate high SWR with negligible loss at our operating frequencies. We also use an appropriate balanced line, low insertion loss, open wire tuner to match our transmitter to the feedline.
All inefficiencies that can be reduced, have been made insignificant. This same approach can be used for antennas of several non–resonate types. Needless to say the graphs would be quite different for different types, bands and mounting heights, but this system is easily adjustable to be a good radiator with little adjustment.
Antennas in this class include the so–called “Zepp” and “double–Zepp” antennas, the off–center fed classic Windom, and any other variation that is a non–resonate dipole.
Lets consider what happens when the dipole is allowed to come in close proximity to other conductors that are near its resonant frequency (e.g. the classic Yagi beam).
We noted that radiating elements very close to ground tend to lower the feedpoint impedance. The same is true in a Yagi configuration where sympathetic radiators positioned close in proximity and parallel to the radiating elements will lower the feedpoint impedance significantly. To fully understand the theory of Yagi beam construction (and other similar dipole based antennas) we should start by understanding how RF currents are generated on beam elements.
At the first of this chapter we noted that currents in the dipole elements flow in only one direction at a time and in the same direction. The illustration depicts RF currents on a three element Yagi where element 2 is the center–fed dipole radiator.
Notice the direction of the arrows indicating direction of current flow for one half of the current cycle. Current in the radiator element 2 (note: the radiator, often called the driven element, is center fed but may also incorporate matching components) creates a magnetic field that induces current electromagnetically in element 3 (the director ) and element 1 (the reflector ). The distance between each of the elements determines whether the resulting radiation pattern is subtractive or additive in a particular direction. Common spacing places the reflector at about .15 wavelength behind and the director about .14 wavelength in front of the radiator element. This relationship is important if radiation pattern directionality is to be established that is common for Yagi style antennae. Of course, other spacing arrangements are possible but yield differing results. Elements can be spaced to maximize gain or maximize front to back directivity. Compromises are often made to one or the other to arrive at a suitable design.
Placing sympathetic, passive elements (meaning no power is supplied by the coax to these elements) close to the dipole radiator in this way produces a more directional radiation pattern versus the dipole alone. The next illustration depicts the radiation pattern of a three element yagi at our test frequency and a common height of 33 feet.
Now we can see why the yagi is one of the most popular directional antennae sold in the US. The directional gain has increased dramatically, and the takeoff angle has lowered to 26.5 degrees. This antenna style is even more effective if given more height. The takeoff angle (the elevation angle at which there is maximum radiation) lowers and impedance increases.
This style of directional antenna while effective, presents a feedpoint matching challenge. You should notice the feedpoint impedance is only 25 ohms without matching. Application of creative matching techniques (like the tuned hairpin stub or balanced “T”) can bring this impedance very close to our desire for 50 ohms at the coax and allow for adjustments where height and environment require. Lets look at the three element yagi at the proper height and properly matched.
In this scenario, we can see a different radiation pattern than before. Now there are two forward lobes of radiation. One at 14.5 degrees and another at about 47 degrees. This is quite convenient for both long and short hop propagational conditions. Maximum gain has increased by almost 3 db.
Construction is relatively simple, having only three elements. Homebrew
plans for such an antenna are available from a number of sources and
online. Commercial versions of this antenna have been available for
decades at reasonable costs.
More on this subject later.
Just a reminder for those who may not have followed this column from the beginning. This series is designed to be a thumbnail treatise of a very complex subject area. It is designed to be a reference view of the covered subjects and not an in–depth discussion. We have avoided the finer points of math and technology in order to bring forward information relevant and important to making day to day decisions in the ham shack.
Further study is recommended in the text of the ARRL Handbook and the ARRL Antenna Book. A continuing education course is also offered by the ARRL on antenna modeling with computers. This course is very helpful and enlightening – well worth the time. The course material is in print form as well. It is available separately from ARRL Publications.